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19-2929; Rev 0; 8/03
1200MHz to 2500MHz Adjustable RF Predistorter
General Description
The MAX2009 adjustable RF predistorter is designed to improve power amplifier (PA) adjacent-channel power rejection (ACPR) by introducing gain and phase expansion in a PA chain to compensate for the PA's gain and phase compression. With its +23dBm maximum input power level and wide adjustable range, the MAX2009 can provide up to 12dB of ACPR improvement for power amplifiers operating in the 1200MHz to 2500MHz frequency band. Lower frequencies of operation can be achieved with this IC's counterpart, the MAX2010. The MAX2009 is unique in that it provides up to 7dB of gain expansion and 24 of phase expansion as the input power is increased. The amount of expansion is configurable through two independent sets of control: one set adjusts the gain expansion breakpoint and slope, while the second set controls the same parameters for phase. With these settings in place, the linearization circuit can be run in either a static set-andforget mode, or a more sophisticated closed-loop implementation can be employed with real-time software-controlled distortion correction. Hybrid correction modes are also possible using simple lookup tables to compensate for factors such as PA temperature drift or PA loading. The MAX2009 comes in a 28-pin thin QFN exposed pad (EP) package (5mm x 5mm) and is specified for the extended (-40C to +85C) temperature range. o o o o o o o o o o o o o
Features
Up to 12dB ACPR Improvement* Independent Gain and Phase Expansion Controls Gain Expansion Up to 7dB Phase Expansion Up to 24 1200MHz to 2500MHz Frequency Range Exceptional Gain and Phase Flatness Group Delay <1.3ns (Gain and Phase Sections Combined) 0.04ns Group Delay Ripple Over a 100MHz Band Capable of Handling Input Drives Up to +23dBm On-Chip Temperature Variation Compensation Single +5V Supply Low Power Consumption: 75mW (typ) Fully Integrated into Small 28-Pin Thin QFN Package
MAX2009
*Performance dependent on amplifier, bias, and modulation.
Ordering Information
PART MAX2009ETI-T TEMP RANGE -40C to +85C PIN-PACKAGE 28 Thin QFN-EP*
*EP = Exposed paddle.
Applications
WCDMA/UMTS, cdma2000, DCS1800, and PCS1900 Base Stations Feed-Forward PA Architectures Digital Baseband Predistortion Architectures Military Applications WLAN Applications
GND* ING GND* GND* OUTP GND* 2 3 4 5 6 7 8 GND* 9 INP 10 GND* GND* 1 OUTG GND* GND*
Functional Diagram/ Pin Configuration
GND* 22 21 VCCG GAIN CONTROL 20 GND* 19 PBRAW 18 PBEXP 17 PBIN PHASE CONTROL 16 GND* 15 VCCP 11 PFS1 12 PFS2 13 PDCS1 14 PDCS2 GCS GBP 23 GFS 24
28
27
26
25
MAX2009
*INTERNALLY CONNECTED TO EXPOSED GROUND PADDLE.
________________________________________________________________ Maxim Integrated Products
1
For pricing, delivery, and ordering information, please contact Maxim/Dallas Direct! at 1-888-629-4642, or visit Maxim's website at www.maxim-ic.com.
1200MHz to 2500MHz Adjustable RF Predistorter MAX2009
ABSOLUTE MAXIMUM RATINGS
VCCG, VCCP to GND ..............................................-0.3V to +5.5V ING, OUTG, GCS, GFS, GBP to GND......-0.3V to (VCCG + 0.3V) INP, OUTP, PFS_, PDCS_, PBRAW, PBEXP, PBIN to GND ............................-0.3V to (VCCP + 0.3V) Input (ING, INP, OUTP, OUTG) Level ............................+23dBm PBEXP Output Current ........................................................1mA Continuous Power Dissipation (TA = +70C) 28-Pin Thin QFN-EP (derate 21mW/C above +70C) ...............................1667mW Operating Temperature Range ...........................-40C to +85C Junction Temperature ......................................................+150C Storage Temperature Range .............................-65C to +150C Lead Temperature (soldering 10s) ..................................+300C
Stresses beyond those listed under "Absolute Maximum Ratings" may cause permanent damage to the device. These are stress ratings only, and functional operation of the device at these or any other conditions beyond those indicated in the operational sections of the specifications is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability.
DC ELECTRICAL CHARACTERISTICS
(MAX2009 EV kit; VCCG = VCCP = +4.75V to +5.25V; no RF signal applied; INP, ING, OUTP, OUTG are AC-coupled and terminated to 50; VPF_S1 = open; PBEXP shorted to PBRAW; VPDCS1 = VPDCS2 = 0.8V; VPBIN = VGBP = VGCS = GND; VGFS = VCCG; TA = -40C to +85C. Typical values are at VCCG = VCCP = +5.0V, TA = +25C, unless otherwise noted.)
PARAMETER Supply Voltage Supply Current Analog Input Voltage Range VCCG, VCCP VCCP VCCG PBIN, PBRAW GBP, GFS, GCS VGFS = VGCS = VPBRAW = 0V Analog Input Current Logic-Input High Voltage Logic-Input Low Voltage Logic Input Current VGBP = 0 to +5V VPBIN = 0 to +5V PDCS1, PDCS2 (Note 1) PDCS1, PDCS2 (Note 1) -2 0 0 -2 -100 -100 2.0 0.8 +2 CONDITIONS MIN 4.75 5.8 10 TYP MAX 5.25 7 12.1 VCCP VCCG +2 +170 +220 V V A A UNITS V mA V
2
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1200MHz to 2500MHz Adjustable RF Predistorter
AC ELECTRICAL CHARACTERISTICS
(MAX2009 EV kit, VCCG = VCCP = +4.75V to +5.25V, 50 environment, PIN = -20dBm, fIN = 1200MHz to 2500MHz, VGCS = +1.0V, VGFS = +5.0V, VGBP = +1.2V, VPBIN = VPDCS1 = VPDCS2 = 0V, VPF_S1 = +5V, VPBRAW = VPBEXP, TA = -40C to +85C. Typical values are at fIN = 2140MHz, VCCG = VCCP = +5V, TA = +25C, unless otherwise noted.) (Notes 1, 2)
PARAMETER Operating Frequency Range VSWR PHASE CONTROL SECTION Nominal Gain Gain Variation Over Temperature Gain Flatness Phase-Expansion Breakpoint Maximum Phase-Expansion Breakpoint Minimum Phase-Expansion Breakpoint Variation Over Temperature TA = -40C to +85C Over a 100MHz band VPBIN = +5V VPBIN = 0V TA = -40C to +85C VPF_S1 = +5V, VPDCS1 = VPDCS2 = 0V, PIN = -20 dBm to +23 dBm Phase Expansion VPDCS1 = 5V, VPDCS2 = 0V, VPF_S1 = +1.5V VPDCS1 = 0V, VPDCS2 = 5V, VPF_S1 = +1.5V VPF_S1 = 0V, VPDCS1 = VPDCS2 = +5V, PIN = -20dBm to +23dBm Phase-Expansion Slope Maximum Phase-Expansion Slope Minimum Phase Slope Variation Over Temperature Phase Ripple Noise Figure Absolute Group Delay Group Delay Ripple Parasitic Gain Expansion Interconnects de-embedded Over a 100MHz band PIN = -20dBm to +23dBm PIN = +15dBm VPF_S1 = 0V, VPDCS1 = VPDCS2 = +5V, PIN = +15dBm PIN = +15dBm, TA = -40C to +85C Over a 100MHz band, deviation from linear phase -7.5 -1.4 0.1 23 3.7 1.3 23.7 14.2 9.2 7.6 1.2 0.4 -0.1 0.15 7.5 0.7 0.03 0.9 Degrees /dB Degrees /dB Degrees /dB Degrees dB ns ns dB Degrees dB dB dB dBm dBm dB ING, INP, OUTG, OUTP CONDITIONS MIN 1200 1.3:1 TYP MAX 2500 UNITS MHz
MAX2009
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3
1200MHz to 2500MHz Adjustable RF Predistorter MAX2009
AC ELECTRICAL CHARACTERISTICS (continued)
(MAX2009 EV kit, VCCG = VCCP = +4.75V to +5.25V, 50 environment, PIN = -20dBm, fIN = 1200MHz to 2500MHz, VGCS = +1.0V, VGFS = +5.0V, VGBP = +1.2V, VPBIN = VPDCS1 = VPDCS2 = 0V, VPF_S1 = +5V, VPBRAW = VPBEXP, TA = -40C to +85C. Typical values are at fIN = 2140MHz, VCCG = VCCP = +5V, TA = +25C, unless otherwise noted.) (Notes 1, 2)
PARAMETER GAIN CONTROL SECTION -16 Nominal Gain Gain Variation Over Temperature Gain Flatness Gain-Expansion Breakpoint Maximum Gain-Expansion Breakpoint Minimum Gain-Expansion Breakpoint Variation Over Temperature Gain Expansion Gain-Expansion Slope Gain Slope Variation Over Temperature Noise Figure Absolute Group Delay Group Delay Ripple Phase Ripple Parasitic Phase Expansion Interconnects de-embedded Over a 100MHz band Over a 100MHz band, deviation from linear phase PIN = -20dBm to +23dBm VGCS = 0V, VGFS = +5V VGCS = +5V, VGFS = 0V TA = -40C to +85C Over a 100MHz band VGBP = +5V VGBP = +0.5V TA = -40C to +85C VGFS = +5V, PIN = -20dBm to +23dBm VGFS = 0V, PIN = -20dBm to +23dBm VGFS = +5V, PIN = +15dBm VGFS = +0V, PIN = +15dBm PIN = +15dBm, TA = -40C to +85C -23 -8.5 -1 0.3 23 -3 -0.3 6.6 3.6 0.5 0.26 -0.04 16 0.61 0.01 0.07 5 dB dB dBm dBm dB dB dB/dB dB/dB dB ns ns Degrees Degrees dB CONDITIONS MIN TYP MAX UNITS
Note 1: Guaranteed by design and characterization. Note 2: All limits reflect losses and characteristics of external components shown in the Typical Application Circuit, unless otherwise noted.
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1200MHz to 2500MHz Adjustable RF Predistorter
Typical Operating Characteristics
Phase Control Section
(MAX2009 EV kit, VCCP = +5.0V, PIN = -20dBm, VPBIN = 0V, VPF_S1 = +5.0V, VPDCS1 = VPDCS2 = 0V, fIN = 2140MHz, TA = +25C, unless otherwise noted.)
SUPPLY CURRENT vs. SUPPLY VOLTAGE
6.2 6.1 SUPPLY CURRENT (mA) 6.0 5.9 5.8 5.7 5.6 5.5 5.4 5.3 4.75 4.85 4.95 5.05 5.15 5.25 SUPPLY VOLTAGE (V) 35 B 40 1.1 2.1 2.3 1.9 FREQUENCY (GHz) A = VPDCS1 = VPDCS2 = VPF_S1 = 0V B = VPDCS1 = VPDCS2 = 0V, VPF_S1 = 5V C = VPDCS1 = VPDCS2 = 5V, VPF_S1 = 0V D = VPDCS1 = VPDCS2 = VPF_S1 = 5V 1.3 1.5 1.7 2.5 40 1.1 1.7 1.9 2.1 2.3 FREQUENCY (GHz) A = VPDCS1 = VPDCS2 = VPF_S1 = 0V B = VPDCS1 = VPDCS2 = 0V, VPF_S1 = 5V C = VPDCS1 = VPDCS2 = 5V, VPF_S1 = 0V D = VPDCS1 = VPDCS2 = VPF_S1 = 5V 1.3 1.5 2.5 35 TA = -40C TA = +85C TA = +25C
MAX2009TOC01
MAX2009
SMALL-SIGNAL INPUT RETURN LOSS vs. FREQUENCY
MAX2009TOC02
SMALL-SIGNAL OUTPUT RETURN LOSS vs. FREQUENCY
5 OUTPUT RETURN LOSS (dB) 10 15 20 25 30 D B C
MAX2009TOC03
6.3
0 5 INPUT RETURN LOSS (dB) 10 15 D 20 25 30 A C
0
A
LARGE-SIGNAL INPUT RETURN LOSS vs. FREQUENCY
MAX2009TOC04
LARGE-SIGNAL OUTPUT RETURN LOSS vs. FREQUENCY
5 OUTPUT RETURN LOSS (dB) 10 GAIN (dB) 15 20 25 30 35 40 2.5 1.1 1.7 1.9 2.1 2.3 FREQUENCY (GHz) A = VPDCS1 = VPDCS2 = VPF_S1 = 0V B = VPDCS1 = VPDCS2 = 0V, VPF_S1 = 5V C = VPDCS1 = VPDCS2 = 5V, VPF_S1 = 0V D = VPDCS1 = VPDCS2 = VPF_S1 = 5V 1.3 1.5 2.5 B D C PIN = +15dBm
MAX2009TOC05
SMALL-SIGNAL GAIN vs. FREQUENCY
-5.5 -6.0 -6.5 -7.0 -7.5 -8.0 -8.5 TA = +85C TA = +25C TA = -40C
MAX2009TOC06
0 PIN = +15dBm 5 INPUT RETURN LOSS (dB) 10 15 20 25 30 35 40 1.1 1.7 1.9 2.1 2.3 FREQUENCY (GHz) A = VPDCS1 = VPDCS2 = VPF_S1 = 0V B = VPDCS1 = VPDCS2 = 0V, VPF_S1 = 5V C = VPDCS1 = VPDCS2 = 5V, VPF_S1 = 0V D = VPDCS1 = VPDCS2 = VPF_S1 = 5V 1.3 1.5 B A D C
0
-5.0
A
-9.0 -9.5 -10.0 1.1 1.3 1.5 1.7 1.9 2.1 2.3 2.5 FREQUENCY (GHz)
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1200MHz to 2500MHz Adjustable RF Predistorter MAX2009
Typical Operating Characteristics (continued)
Phase Control Section (continued)
(MAX2009 EV kit, VCCP = +5.0V, PIN = -20dBm, VPBIN = 0V, VPF_S1 = +5.0V, VPDCS1 = VPDCS2 = 0V, fIN = 2140MHz, TA = +25C, unless otherwise noted.)
SMALL-SIGNAL GAIN vs. FREQUENCY
MAX2009TOC07
SMALL-SIGNAL GAIN vs. COARSE SLOPE
MAX2009TOC08
SMALL-SIGNAL GAIN vs. COARSE SLOPE
TA = -40C -6.0
MAX2009TOC09
-5.0 -5.5 -6.0 -6.5 GAIN (dB) VCCP = 4.75V, 5.0V, 5.25V
-5.5
-5.5
-6.0
GAIN (dB)
VPF_S1 = 1.5V VPF_S1 = 5V
-7.5 -8.0 -8.5 -9.0 -9.5 -10.0 1.1 1.3 1.5 1.7 1.9 2.1 2.3 2.5 FREQUENCY (GHz)
-7.0
GAIN (dB)
-7.0
-6.5
-6.5
TA = +25C
-7.0 TA = +85C
-7.5 VPF_S1 = 0V -8.0 PDCS1 = 0, PDCS2 = 0 PDCS1 = 5, PDCS1 = 0, PDCS2 = 0 PDCS2 = 5 COARSE SLOPE (V) PDCS1 = 5, PDCS2 = 5
-7.5
-8.0 PDCS1 = 0, PDCS2 = 0
PDCS1 = 5, PDCS2 = 0
PDCS1 = 0, PDCS2 = 5
PDCS1 = 5, PDCS2 = 5
COARSE SLOPE (V)
GROUP DELAY vs. FREQUENCY
MAX2009TOC10
NOISE FIGURE vs. FREQUENCY
MAX2009TOC11
SUPPLY CURRENT vs. INPUT POWER
MAX2009TOC12
0.85 0.80 D 0.75 DELAY (ns) 0.70 0.65 0.60 0.55 C 0.50 1.1 2.1 2.3 1.9 FREQUENCY (GHz) A = VPDCS1 = VPDCS2 = VPF_S1 = 0V B = VPDCS1 = VPDCS2 = 0V, VPF_S1 = 5V C = VPDCS1 = VPDCS2 = 5V, VPF_S1 = 0V D = VPDCS1 = VPDCS2 = VPF_S1 = 5V 1.3 1.5 1.7 B A
9.5 9.0 8.5 NOISE FIGURE (dB) 8.0 7.5 7.0 6.5 6.0 5.5 5.0 C A D B
6.00 5.95 SUPPLY CURRENT (mA) 5.90 5.85 C 5.80 D 5.75 5.70 E A B
2.5
1.5
2.3 2.1 FREQUENCY (GHz) A = VPDCS1 = VPDCS2 = VPF_S1 = 0V B = VPDCS1 = VPDCS2 = 0V, VPF_S1 = 5V C = VPDCS1 = VPDCS2 = 5V, VPF_S1 = 0V D = VPDCS1 = VPDCS2 = VPF_S1 = 5V
1.7
1.9
2.5
0
4
8
12
16
20
24
INPUT POWER (dBm) D = VPBIN = 1.5V A = VPBIN = 0V E = VPBIN = 3.0V B = VPBIN = 0.5V C = VPBIN = 1.0V
INTERCONNECTS DE-EMBEDDED
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1200MHz to 2500MHz Adjustable RF Predistorter
Typical Operating Characteristics (continued)
Phase Control Section (continued)
(MAX2009 EV kit, VCCP = +5.0V, PIN = -20dBm, VPBIN = 0V, VPF_S1 = +5.0V, VPDCS1 = VPDCS2 = 0V, fIN = 2140MHz, TA = +25C, unless otherwise noted.)
MAX2009
GAIN EXPANSION vs. INPUT POWER
MAX2009TOC13
PHASE EXPANSION vs. INPUT POWER
MAX2009TOC14
GAIN EXPANSION vs. INPUT POWER
-6.2 -6.4 -6.6 GAIN (dB) -6.8 -7.0 -7.2 -7.4 -7.6 -7.8 A B C D
MAX2009TOC15
-6.0 -6.2 -6.4 -6.6 GAIN (dB) -6.8 -7.0 -7.2 B -7.4 -7.6 A -7.8 -7 -2 3 8 13 18 C F E D
190
-6.0
C 180 PHASE (DEGREES) B 170 A D 160 E F 150
23
-7
-2
3
8
13
18
23
-7
-2
3
8
13
18
23
INPUT POWER (dBm) D = VPBIN = 1.5V A = VPBIN = 0V E = VPBIN = 2.0V B = VPBIN = 0.5V C = VPBIN = 1.0V F = VPBIN = 2.5V
INPUT POWER (dBm) D = VPBIN = 1.5V A = VPBIN = 0V E = VPBIN = 2.0V B = VPBIN = 0.5V C = VPBIN = 1.0V F = VPBIN = 2.5V
INPUT POWER (dBm) C = VPDCS1 = 0V, VPDCS2 = 5V A = VPDCS1 = VPDCS2 = 0V B = VPDCS1 = 5V, VPDCS2 = 0V D = VPDCS1 = VPDCS2 = 5V
GAIN EXPANSION vs. INPUT POWER
-6.2 -6.4 -6.6 GAIN (dB) -6.8 -7.0 B -7.2 -7.4 F -7.6 -7.8 -7 -2 3 8 13 18 23 INPUT POWER (dBm) E = VPF_S1 = 2.0V A = VPF_S1 = 0V B = VPF_S1 = 0.5V F = VPF_S1 = 5.0V C = VPF_S1 = 1.0V VPDCS1 = 5.0V D = VPF_S1 = 1.5V 150 -7 A C E D
MAX2009TOC16
PHASE EXPANSION vs. INPUT POWER
MAX2009TOC17
PHASE EXPANSION vs. INPUT POWER
MAX2009TOC18
-6.0
190
190
180 PHASE (DEGREES) E 170 D
PHASE (DEGREES)
F
180 B 170
A
160 C A -2 3 8 13 B
160 D 150 18 23 -7 -2 3 8 13
C
18
23
INPUT POWER (dBm) D = VPF_S1 = 1.5V A = VPF_S1 = 0V B = VPF_S1 = 0.5V E = VPF_S1 = 2.0V C = VPF_S1 = 1.0V F = VPF_S1 = 5.0V VPDCS1 = 5.0V
INPUT POWER (dBm) C = VPDCS1 = 0V, VPDCS2 = 5V A = VPDCS1 = VPDCS2 = 0V D = VPDCS1 = VPDCS2 = 5V B = VPDCS1 = 5V, VPDCS2 = 0V
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1200MHz to 2500MHz Adjustable RF Predistorter MAX2009
Typical Operating Characteristics (continued)
Phase Control Section (continued)
(MAX2009 EV kit, VCCP = +5.0V, PIN = -20dBm, VPBIN = 0V, VPF_S1 = +5.0V, VPDCS1 = VPDCS2 = 0V, fIN = 2140MHz, TA = +25C, unless otherwise noted.)
GAIN EXPANSION vs. INPUT POWER
MAX2009TOC19
PHASE EXPANSION vs. INPUT POWER
VPDCS1 = 5.0, VPF_S1 = 1.5V
MAX2009TOC20
-5.3
VPDCS1 = 5.0, VPF_S1 = 1.5V
180 175 PHASE (DEGREES) 170 165 160 155
-5.8 TA = -40C GAIN (dB) -6.3
-6.8
TA = +25C
TA = -40C TA = +25C TA = +85C
-7.3 TA = +85C -7.8 -7 -2 3 8 13 18 23 INPUT POWER (dBm)
150 -7 -2 3 8 13 18 23 INPUT POWER (dBm)
Typical Operating Characteristics
Gain Control Section
(MAX2009 EV kit, VCCG = +5.0V, PIN = -20dBm, VGBP = +1.2V, VGFS = +5.0V, VGCS = +1.0V, fIN = 2140MHz, TA = +25C, unless otherwise noted.)
SMALL-SIGNAL INPUT RETURN LOSS vs. FREQUENCY
MAX2009TOC22
SUPPLY CURRENT vs. SUPPLY VOLTAGE
MAX2009TOC21
SMALL-SIGNAL OUTPUT RETURN LOSS vs. FREQUENCY
5 OUTPUT RETURN LOSS (dB) 10 15 20 A 25 30 35 40 B
MAX2009TOC23
9.4 9.2 SUPPLY CURRENT (mA) 9.0 8.8 8.6 8.4 8.2 8.0 4.75 4.85 4.95 5.05 5.15 TA = +85C TA = +25C
0 5 INPUT RETURN LOSS (dB) D 10 15 20 25 30 35 40 A B C
0 D C
TA = -40C 5.25
1.1
1.3
1.5
1.7
1.9
2.1
2.3
2.5
1.1
1.3
1.5
1.7
1.9
2.1
2.3
2.5
SUPPLY VOLTAGE (V)
FREQUENCY (GHz) A = VGCS = 0V, VGFS = 0V C = VGCS = 5V, VGFS = 0V B = VGCS = 0V, VGFS = 5V D = VGCS = 5V, VGFS = 5V
FREQUENCY (GHz) A = VGCS = 0V, VGFS = 0V C = VGCS = 5V, VGFS = 0V B = VGCS = 0V, VGFS = 5V D = VGCS = 5V, VGFS = 5V
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1200MHz to 2500MHz Adjustable RF Predistorter
Typical Operating Characteristics (continued)
Gain Control Section (continued)
(MAX2009 EV kit, VCCG = +5.0V, PIN = -20dBm, VGBP = +1.2V, VGFS = +5.0V, VGCS = +1.0V, fIN = 2140MHz, TA = +25C, unless otherwise noted.)
LARGE-SIGNAL INPUT RETURN LOSS vs. FREQUENCY
MAX2009TOC24
MAX2009
LARGE-SIGNAL OUTPUT RETURN LOSS vs. FREQUENCY
MAX2009TOC25
SMALL-SIGNAL GAIN vs. FREQUENCY
-13 -14 GAIN (dB) -15 -16 -17 TA = +25C TA = +85C TA = -40C
MAX2009TOC26
0 PIN = +15dBm 5 INPUT RETURN LOSS (dB) 10 15 20 25 30 35 40 1.1 1.3 1.5 1.7 1.9 2.1 2.3 A B C D
0 PIN = +15dBm 5 OUTPUT RETURN LOSS (dB) 10 15 20 25 30 35 40 A B C D
-12
-18 -19
2.5
1.1
1.3
1.5
1.7
1.9
2.1
2.3
2.5
-20 1.1 1.3 1.5 1.7 1.9 2.1 2.3 2.5 FREQUENCY (GHz)
FREQUENCY (GHz) A = VGCS = 0V, VGFS = 0V C = VGCS = 5V, VGFS = 0V B = VGCS = 0V, VGFS = 5V D = VGCS = 5V, VGFS = 5V
FREQUENCY (GHz) A = VGCS = 0V, VGFS = 0V C = VGCS = 5V, VGFS = 0V B = VGCS = 0V, VGFS = 5V D = VGCS = 5V, VGFS = 5V
SMALL-SIGNAL GAIN vs. FREQUENCY
MAX2009TOC27
SMALL-SIGNAL GAIN vs. VGCS
MAX2009TOC28
SMALL-SIGNAL GAIN vs. VGCS
-9 -11 -13 GAIN (dB) -15 -17 -19 -21 -23 -25 TA = +25C TA = -40C TA = +85C
MAX2009TOC29
-12 VCCG = 4.75V, 5.0V, 5.25V -13 -14 GAIN (dB)
-7 -9 -11 -13 GAIN (dB) -15 -17 -19 -21 -23 -25
VGFS = 0V, 1.5V, 5.0V
-7
-15 -16 -17 -18 -19 -20 1.1 1.3 1.5 1.7 1.9 2.1 2.3 2.5 FREQUENCY (GHz)
0
1
2 VGCS (V)
3
4
5
0
1
2 VGCS (V)
3
4
5
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9
1200MHz to 2500MHz Adjustable RF Predistorter MAX2009
Typical Operating Characteristics (continued)
Gain Control Section (continued)
(MAX2009 EV kit, VCCG = +5.0V, PIN = -20dBm, VGBP = +1.2V, VGFS = +5.0V, VGCS = +1.0V, fIN = 2140MHz, TA = +25C, unless otherwise noted.)
GROUP DELAY vs. FREQUENCY
MAX2009TOC30
NOISE FIGURE vs. FREQUENCY
B 24 22 NOISE FIGURE (dB) 20 18 16 14 12 10 8 E D 5 1.5 1.7 0 C A
MAX2009TOC31
SUPPLY CURRENT vs. INPUT POWER
MAX2009TOC32
0.75 0.70 D 0.65 DELAY (ns) 0.60 0.55 B 0.50 0.45 1.1 1.3 1.5 1.7 1.9 2.1 2.3
26
30
25 SUPPLY CURRENT (mA)
20 B 15
A C
A
C
E 10 D
6 2.5 FREQUENCY (GHz) A = VGCS = 0V, VGFS = 0V C = VGCS = 5V, VGFS = 0V B = VGCS = 0V, VGFS = 5V D = VGCS = 5V, VGFS = 5V INTERCONNECTS DE-EMBEDDED 2.1 2.3 2.5 1.9 FREQUENCY (GHz) D = VGCS = 5V, VGFS = 0V A = VGCS = 0V, VGFS = 0V E = VGCS = 5V, VGFS = 5V B = VGCS = 0V, VGFS = 5V C = VGCS = 1.5V, VGFS = 5V
12 16 20 24 8 INPUT POWER (dBm) A = VGBP = 0V D = VGBP = 1.5V B = VGBP = 0.5V E = VGBP = 3.0V C = VGBP = 1.0V
4
GAIN EXPANSION vs. INPUT POWER
MAX2009TOC33
PHASE EXPANSION vs. INPUT POWER
MAX2009TOC34
-7 -9 -11
A
190 180 PHASE (DEGREES) 170 AB 160 150 140 H 130 G -2 C D
B GAIN (dB) -13 -15 -17 -19 -21 -23 -7 C
D
E
F
GH
F
E
8 13 18 23 3 INPUT POWER (dBm) A = VGBP = 0V E = VGBP = 2.0V B = VGBP = 0.5V F = VGBP = 2.5V C = VGBP = 1.0V G = VGBP = 3.5V D = VGBP = 1.5V H = VGBP = 5.0V
-2
-7
8 13 18 23 3 INPUT POWER (dBm) A = VGBP = 0V E = VGBP = 2.0V B = VGBP = 0.5V F = VGBP = 2.5V C = VGBP = 1.0V G = VGBP = 3.5V D = VGBP = 1.5V H = VGBP = 5.0V
10
______________________________________________________________________________________
1200MHz to 2500MHz Adjustable RF Predistorter
Typical Operating Characteristics (continued)
Gain Control Section (continued)
(MAX2009 EV kit, VCCG = +5.0V, PIN = -20dBm, VGBP = +1.2V, VGFS = +5.0V, VGCS = +1.0V, fIN = 2140MHz, TA = +25C, unless otherwise noted.)
GAIN EXPANSION vs. INPUT POWER
MAX2009TOC35
MAX2009
GAIN EXPANSION vs. INPUT POWER
E -9 -11 PHASE (DEGREES) F
MAX2009TOC36
PHASE EXPANSION vs. INPUT POWER
MAX2009TOC37
-7 -9 -11 GAIN (dB) F E
-7
190 180 A, B 170 160 150 D 140 F 130
-15 -17 -19 -21 -23 -7
C
A, B D
GAIN (dB)
-13
-13 -15 -17 -19 -21 -23 A, B D C
C E
8 13 18 23 3 INPUT POWER (dBm) A = VGFS = 0V D = VGFS = 1.5V B = VGFS = 0.5V E = VGFS = 2.0V C = VGFS = 1.0V F = VGFS = 5.0V
-2
-7
8 13 18 23 3 INPUT POWER (dBm) A = VGCS = 0V D = VGCS = 1.5V B = VGCS = 0.5V E = VGCS = 2.0V C = VGCS = 1.0V F = VGCS = 2.5V
-2
-7
8 13 18 23 3 INPUT POWER (dBm) A = VGCS = 0V D = VGCS = 1.5V B = VGCS = 0.5V E = VGCS = 2.0V C = VGCS = 1.0V F = VGCS = 2.5V
-2
PHASE EXPANSION vs. INPUT POWER
MAX2009TOC38
GAIN EXPANSION vs. INPUT POWER
MAX2009TOC39
PHASE EXPANSION vs. INPUT POWER
158 156 PHASE (DEGREES) 154 152 150 148 146 144 142 140 TA = +85C TA = -40C TA = +25C
MAX2009TOC40
190 180 PHASE (DEGREES) 170
-8 -9 -10 -11 GAIN (dB) TA = -40C
160
160 150 140 130 -7 A, B
F
E
-12 -13 -14 TA = +25C TA = +85C
C
D
-15 -16 -17
8 13 18 23 3 INPUT POWER (dBm) A = VGFS = 0V D = VGFS = 1.5V B = VGFS = 0.5V E = VGFS = 2.0V C = VGFS = 1.0V F = VGFS = 5.0V
-2
-7
-2
8 13 3 INPUT POWER (dBm)
18
23
-7
-2
8 13 3 INPUT POWER (dBm)
18
23
______________________________________________________________________________________
11
1200MHz to 2500MHz Adjustable RF Predistorter MAX2009
Pin Description
PIN 1, 2, 4, 5, 7, 8, 10, 16, 20, 22, 26, 28 3 6 9 11 12 13 14 15 17 18 19 21 23 24 25 27 EP NAME GND FUNCTION Ground. Internally connected to the exposed paddle. RF Gain Input. Connect ING to a coupling capacitor if it is not connected to OUTP. ING is interchangeable with OUTG. RF Phase Output. Connect OUTP to a coupling capacitor if it is not connected to INP. OUTP is interchangeable with INP. RF Phase Input. Connect INP to a coupling capacitor. This pin is interchangeable with OUTP. Fine Phase-Slope Control Input 1. See the Typical Application Circuit. Fine Phase-Slope Control Input 2. See the Typical Application Circuit. Digital Coarse Phase-Slope Control Range Input 1. Set to logical zero for the steepest slope. Digital Coarse Phase-Slope Control Range Input 2. Set to logical zero for the steepest slope. Phase-Control Supply Voltage. Bypass with a 0.01F capacitor to ground as close to the device as possible. Phase section can operate without VCCG. Phase Breakpoint Control Input Phase Expansion Output. Connect PBEXP to PBRAW to use PBIN as the breakpoint control voltage. Uncompensated Phase Breakpoint Input Gain-Control Supply Voltage. Bypass with a 0.01F capacitor to ground as close to the device as possible. Gain section can operate without VCCP. Gain Breakpoint Control Input Fine Gain-Slope Control Input Coarse Gain-Slope Control Input RF Gain Output. Connect OUTG to a coupling capacitor. OUTG is interchangeable with ING. Exposed Ground Paddle. Solder EP to the ground plane.
ING OUTP INP PFS1 PFS2 PDCS1 PDCS2 VCCP PBIN PBEXP PBRAW VCCG GBP GFS GCS OUTG GND
Detailed Description
The MAX2009 adjustable predistorter can provide up to 12dB of ACPR improvement for high-power amplifiers by introducing gain and phase expansion to compensate for the PA's gain and phase compression. The MAX2009 enables real-time software-controlled distortion correction, as well as set-and-forget tuning through the adjustment of the expansion starting point (breakpoint) and the rate of expansion (slope). The gain and phase break-
points can be set over a 20dB input power range. The phase expansion slope is variable from 0.3/dB to 2.0/dB and can be adjusted for a maximum of 24 of phase expansion. The gain expansion slope is variable from 0.1dB/dB to 0.6dB/dB and can be adjusted for a maximum of 7dB gain expansion. The following sections describe the tuning methodology best implemented with a class A amplifier. Other classes of operation may require significantly different settings.
12
______________________________________________________________________________________
1200MHz to 2500MHz Adjustable RF Predistorter
Phase Expansion Circuitry
Figure 1 shows a typical PA's phase behavior with respect to input power. For input powers less than the breakpoint level, the phase remains relatively constant. As the input power becomes greater than the breakpoint level, the phase begins to compress and deteriorate the power amplifier's linearity. To compensate for this AM-PM distortion, the MAX2009 provides phase expansion, which occurs at the same breakpoint level but with the opposite slope. The overall result is a flat phase response. Phase Expansion Breakpoint The phase expansion breakpoint is typically controlled by a digital-to-analog converter (DAC) connected through the PBIN pin. The PBIN input voltage range of 0V to VCC corresponds to a breakpoint input power range of 3.7dBm to 23dBm. To achieve optimal performance, the phase expansion breakpoint of the MAX2009 must be set to equal the phase compression breakpoint of the PA. Phase Expansion Slope The phase expansion slope of the MAX2009 must also be adjusted to equal the opposite slope of the PA's phase compression curve. The phase expansion slope of the MAX2009 is controlled by the PFS1, PFS2, PDCS1, and PDCS2 pins. With pins PFS1 and PFS2, AC-coupled and connected to a variable capacitor or varactor diode, the PFS1 and PFS2 pins perform the task of fine tuning the phase expansion slope. Since off-chip varactor diodes are recommended for this function, they must be closely matched and identically biased. A minimum effective capacitance of 2pF to 6pF is required to achieve the full phase slope range as specified in the Electrical Characteristics tables. As shown in Figure 2, the varactors connected to PFS1 and PFS2 are in series with three internal capacitors on each pin. By connecting and disconnecting these internal capacitors, a larger change in phase expansion slope can be achieved through the logic levels presented at the PDCS1 and PDCS2 pins. The phase expansion slope is at its maximum when both VPDCS1 and V PDCS2 equal 0V. The phase tuning has a minimal effect on the small-signal gain.
MAX2009
Gain Expansion Circuitry
In addition to phase compression, the PA also suffers from gain compression (AM-AM) distortion, as shown in Figure 3. The PA gain curve remains flat for input powers below the breakpoint level, and begins to compress at a given rate (slope) for input powers greater than the breakpoint level. To compensate for such gain compression, the MAX2009 generates a gain expansion, which occurs at the same breakpoint level with the opposite slope. The overall result is a flat gain response at the PA output.
PA PHASE COMPRESSION
MAX2009 PHASE EXPANSION
IMPROVED PHASE DISTORTION
SLOPE
PIN (dBm)
PIN (dBm)
COMBINED PHASE (DEGREES)
MAX2009 PHASE (DEGREES)
BREAKPOINT
PA PHASE (DEGREES)
PIN (dBm)
Figure 1. PA Phase Compression Canceled by MAX2009 Phase Expansion
______________________________________________________________________________________
13
1200MHz to 2500MHz Adjustable RF Predistorter MAX2009
PFS1
PF_S1 PHASE-CONTROL CIRCUITRY PFS2
2
PDCS1 SWITCH CONTROL
PDCS2
MAX2009
Figure 2. Simplified Phase Slope Internal Circuitry
PA GAIN COMPRESSION
MAX2009 GAIN EXPANSION
IMPROVED GAIN DISTORTION
BREAKPOINT
SLOPE
PIN (dBm)
PIN (dBm)
COMBINED GAIN (dB)
MAX2009 GAIN (dB)
PA GAIN (dB)
PIN (dBm)
Figure 3. PA Gain Compression Canceled by MAX2009 Gain Expansion
14
______________________________________________________________________________________
1200MHz to 2500MHz Adjustable RF Predistorter
Gain Expansion Breakpoint The gain expansion breakpoint is usually controlled by a DAC connected through the GBP pin. The GBP input voltage range of 0.5V to 5V corresponds to a breakpoint input power range of 3dBm to 23dBm. To achieve the optimal performance, the gain expansion breakpoint of the MAX2009 must be set to equal the gain compression point of the PA. The GBP control has a minimal effect on the small-signal gain when operated from 0.5V to 5V. Gain Expansion Slope In addition to properly setting the breakpoint, the gain expansion slope of the MAX2009 must also be adjusted to compensate for the PA's gain compression. The slope should be set using the following equation: MAX2009 _ SLOPE = where: MAX2009_SLOPE = MAX2009 gain section's slope in dB/dB. PA_SLOPE = PA's gain slope in dB/dB, a negative number for compressive behavior. To modify the gain expansion slope, two adjustments must be made to the biases applied on pins GCS and GFS. Both GCS and GFS have an input voltage range of 0V to VCC, corresponding to a slope of approximately 0.1dB/dB to 0.6dB/dB. The slope is set to maximum when VGCS = 0V and VGFS = +5V, and the slope is at its minimum when VGCS = +5V and VGFS = 0V. Unlike the GBP pin, modifying the gain expansion slope bias on the GCS pin causes a change in the part's insertion loss and noise figure. For example, a smaller slope caused by GCS results in a better insertion loss and lower noise figure. The GFS does not affect the insertion loss. It can provide up to -30% or +30% total slope variation around the nominal slope set by GCS. Large amounts of GCS bias adjustment can also lead to an undesired (or residual) phase expansion/compression behavior. There exists an optimal bias voltage that minimizes this parasitic behavior (typically GCS = 1.0V). Control voltages higher than the optimal result in parasitic phase expansion, lower control voltages result in phase compression. GFS does not contribute to the phase behavior and is preferred for slope control. -PA _ SLOPE 1 + PA _ SLOPE
Applications Information
The following section describes the tuning methodology best implemented with a class A amplifier. Other classes of operation may require significantly different settings.
MAX2009
Gain and Phase Expansion Optimization
The best approach to improve the ACPR of a PA is to first optimize the AM-PM response of the phase section. For most high-frequency LDMOS amplifiers, improving the AM-PM response provides the bulk of the ACPR improvement. Figure 4 shows a typical configuration of the phase tuning circuit. A power sweep on a network analyzer allows quick real-time tuning of the AM-PM response. First, tune PBIN to achieve the phase expansion starting point (breakpoint) at the same point where the PA's phase compression begins. Next, use control pins PF_S1, PDCS1, and PDCS2 to obtain the optimal AM-PM response. The typical values for these pins are shown in Figure 4. To further improve the ACPR, connect the phase output to the gain input through a preamplifier. The preamplifier is used to compensate for the high insertion loss of the gain section. Figure 5 shows a typical application circuit of the MAX2009 with the phase section cascaded to the gain section for further ACPR optimization. Similar to tuning the phase section, first tune the gain expansion breakpoint through the GBP pin and adjust for the desired gain expansion with pins GCS and GFS. To minimize the effect of GCS on the parasitic phase response, minimize the control voltage to around 1V. Some retuning of the AM-PM response may be necessary.
Layout Considerations
A properly designed PC board is an essential part of any high-frequency circuit. To minimize external components, the PC board can be designed to incorporate small values of inductance and capacitance to optimize the input and output VSWR (refer to the MAX2009). The phase section's PFS1 and PFS2 pins are sensitive to external parasitics. Minimize trace lengths and keep varactor diodes close to the pins. Remove the ground plane underneath the traces can further help reduce the parasitic capacitance. For best performance, route the ground pin traces directly to the grounded EP underneath the package. Solder the EP on the bottom of the device package evenly to the board ground plane to provide a heat transfer path along with signal grounding.
______________________________________________________________________________________
15
1200MHz to 2500MHz Adjustable RF Predistorter MAX2009
POWER AMPLIFIER
POUT = 7dBm 6 OUTP ING 3
MAX2009
PREAMPLIFIER 9 INP PIN = 14dBm OUTG 27
11 PFS1 VPF_S1 = 1.5V 12 PFS2 19 PBRAW 18 PBEXP PHASE CONTROL GAIN CONTROL
GBP 23
GFS 24
PBIN PDCS1 PDCS2 VPBIN = 0.8V VPDCS1 = 0V VPDCS2 = 5V 17 13 14
GCS 25
Figure 4. AM-PM Response Tuning Circuit
Power-Supply Bypassing
Bypass each VCC pin with a 0.01F capacitor.
Table 1. Suggested Components of Typical Application Circuit
DESIGNATION VALUE TYPE C1, C6, C8, C10 8.2pF 0.25pF 0402 ceramic capacitors C2, C3 C4, C5 C7, C9 R1, R2 VR1, VR2 1.5pF 0.1pF 0.01F 10% 0.5pF 0.1pF 1k 5% Skyworks SMV1232-079 0402 ceramic capacitors 0603 ceramic capacitors 0402 ceramic capacitors 0402 resistors Hyperabrupt varactor diodes
Exposed Pad RF
The exposed paddle (EP) of the MAX2009's 28-pin thin QFN-EP package provides a low inductance path to ground. It is important that the EP be soldered to the ground plane on the PC board, either directly or through an array of plated via holes.
16
______________________________________________________________________________________
1200MHz to 2500MHz Adjustable RF Predistorter MAX2009
PREAMPLIFIER
GAIN = 7dB 6 OUTP 3 ING
MAX2009
PREAMPLIFIER 9 INP PIN = 14dBm OUTG 27
POWER AMPLIFIER
11 PFS1 VPF_S1 = 1.5V 12 PFS2 19 PBRAW 18 PBEXP PHASE CONTROL GAIN CONTROL
GBP 23
GFS 24
PBIN PDCS1 PDCS2 VPBIN = 0.8V VPDCS1 = 0V VPDCS2 = 5V 17 13 14
GCS 25 VGBP = 1V VGFS = 1.5V VGCS = 1V
Figure 5. MAX2009 Phase and Gain Optimization Circuit
______________________________________________________________________________________
17
1200MHz to 2500MHz Adjustable RF Predistorter MAX2009
Typical Application Circuit
W = 10 mils** L = 160 mils C6
OUTG
GND*
GND*
28 GND* OPTIONAL MATCH COMPENSATION* GND* W = 10 mils** L = 160 mils C8 ING GND* GND* C10 OUTP GND* 1 2 3 4 5 6 7 8
27
26
25
24
23
GND* 22 21 VCCG GND* PBRAW PBEXP PBIN GND* VCCP C4 CONTROL UNIT C5
GCS
GAIN CONTROL
GBP
GFS
POWER AMPLIFER
C7
20 19 18 17
C9
MAX2009
PHASE CONTROL
16 15
PREAMPLIFER
9 INP
10 GND*
11 PFS1
12 PFS2
13 PDCS1
14 PDCS2
GND*
C1
C2
C3
R2 PREAMPLIFER
*INTERNALLY CONNECTED TO EXPOSED GROUND PADDLE. **FR4 0.015in THICK DIELECTRIC. VR1 VR2
R1
Chip Information
TRANSISTOR COUNT: Bipolar: 160 CMOS: 240 PROCESS: BiCMOS
18
______________________________________________________________________________________
1200MHz to 2500MHz Adjustable RF Predistorter
Package Information
(The package drawing(s) in this data sheet may not reflect the most current specifications. For the latest package outline information go to www.maxim-ic.com/packages.)
0.15 C A
MAX2009
D2
C L
D
b D2/2
0.10 M C A B
PIN # 1 I.D.
D/2
0.15 C B
k
PIN # 1 I.D. 0.35x45
E/2 E2/2 E (NE-1) X e
C L
E2
k L
DETAIL A
e (ND-1) X e
C L
C L
L
L
e 0.10 C A 0.08 C
e
C
A1 A3
PROPRIETARY INFORMATION TITLE:
PACKAGE OUTLINE 16, 20, 28, 32L, QFN THIN, 5x5x0.8 mm
APPROVAL DOCUMENT CONTROL NO. REV.
21-0140
C
1 2
COMMON DIMENSIONS
EXPOSED PAD VARIATIONS
NOTES: 1. DIMENSIONING & TOLERANCING CONFORM TO ASME Y14.5M-1994. 2. ALL DIMENSIONS ARE IN MILLIMETERS. ANGLES ARE IN DEGREES. 3. N IS THE TOTAL NUMBER OF TERMINALS. 4. THE TERMINAL #1 IDENTIFIER AND TERMINAL NUMBERING CONVENTION SHALL CONFORM TO JESD 95-1 SPP-012. DETAILS OF TERMINAL #1 IDENTIFIER ARE OPTIONAL, BUT MUST BE LOCATED WITHIN THE ZONE INDICATED. THE TERMINAL #1 IDENTIFIER MAY BE EITHER A MOLD OR MARKED FEATURE. 5. DIMENSION b APPLIES TO METALLIZED TERMINAL AND IS MEASURED BETWEEN 0.25 mm AND 0.30 mm FROM TERMINAL TIP. 6. ND AND NE REFER TO THE NUMBER OF TERMINALS ON EACH D AND E SIDE RESPECTIVELY. 7. DEPOPULATION IS POSSIBLE IN A SYMMETRICAL FASHION. 8. COPLANARITY APPLIES TO THE EXPOSED HEAT SINK SLUG AS WELL AS THE TERMINALS. 9. DRAWING CONFORMS TO JEDEC MO220. 10. WARPAGE SHALL NOT EXCEED 0.10 mm.
PROPRIETARY INFORMATION TITLE:
PACKAGE OUTLINE 16, 20, 28, 32L, QFN THIN, 5x5x0.8 mm
APPROVAL DOCUMENT CONTROL NO. REV.
21-0140
C
2 2
Maxim cannot assume responsibility for use of any circuitry other than circuitry entirely embodied in a Maxim product. No circuit patent licenses are implied. Maxim reserves the right to change the circuitry and specifications without notice at any time.
Maxim Integrated Products, 120 San Gabriel Drive, Sunnyvale, CA 94086 408-737-7600 ____________________ 19 (c) 2003 Maxim Integrated Products Printed USA is a registered trademark of Maxim Integrated Products.
QFN THIN.EPS

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